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800 mhz clock distribution ic, dividers, delay adjust, three outputs ad9513 rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ? 2005 analog devices, inc. all rights reserved. features 1.6 ghz differential clock input 3 programmable dividers divide-by in range from1 to 32 phase select for coarse delay adjust three 800 mhz/250 mhz lvds/cmos clock outputs additive output jitter 300 fs rms time delays up to 11.6 ns device configured with 4-level logic pins space-saving, 32-lead lfcsp applications low jitter, low phase noise clock distribution clocking high speed adcs, dacs, ddss, ddcs, ducs, mxfes high performance wireless transceivers high performance instrumentation broadband infrastructure ate functional block diagram 05595-001 clk clkb syncb rset v sgnd ad9513 vref s10s9s8s7s6s5s4s3s2s1 s0 setup logic out0 out0 b /1. . . /32 lvds/cmos out1 out1 b /1. . . /32 lvds/cmos out2 out2 b /1. . . /32 lvds/cmos ? t figure 1. general description the ad9513 features a three-output clock distribution ic in a design that emphasizes low jitter and phase noise to maximize data converter performance. other applications with demanding phase noise and jitter requirements also benefit from this part. there are three independent clock outputs that can be set to either lvds or cmos levels. these outputs operate to 800 mhz in lvds mode and to 250 mhz in cmos mode. each output has a programmable divider that can be set to divide by a selected set of integers ranging from 1 to 32. the phase of one clock output relative to the other clock output can be set by means of a divider phase select function that serves as a coarse timing adjustment. one of the outputs features a delay element with three selectable full-scale delay values (1.8 ns, 6.0 ns, and 11.6 ns), each with 16 steps of fine adjustment. the ad9513 does not require an external controller for operation or setup. the device is programmed by means of 11 pins (s0 to s10) using 4-level logic. the programming pins are internally biased to ? v s . the vref pin provides a level of ? v s . v s (3.3 v) and gnd (0 v) provide the other two logic levels. the ad9513 is ideally suited for data converter clocking applications where maximum converter performance is achieved by encode signals with subpicosecond jitter. the ad9513 is available in a 32-lead lfcsp and operates from a single 3.3 v supply. the temperature range is ?40c to +85c.
ad9513 rev. 0 | page 2 of 28 table of contents features .............................................................................................. 1 applications....................................................................................... 1 functional block diagram .............................................................. 1 general description ......................................................................... 1 specifications..................................................................................... 3 clock input.................................................................................... 3 clock outputs ............................................................................... 3 timing characteristics ................................................................ 4 clock output phase noise .......................................................... 6 clock output additive time jitter............................................. 8 syncb, vref, and setup pins ................................................... 9 power.............................................................................................. 9 timing diagrams............................................................................ 10 absolute maximum ratings.......................................................... 11 thermal characteristics ............................................................ 11 esd caution................................................................................ 11 pin configuration and function descriptions........................... 12 terminology .................................................................................... 13 typical performance characteristics ........................................... 14 functional description .................................................................. 17 overall.......................................................................................... 17 clk, clkbdifferential clock input ................................... 17 synchronization.......................................................................... 17 power-on sync .................................................................... 17 syncb..................................................................................... 17 rset resistor ............................................................................. 18 vref............................................................................................ 18 setup configuration................................................................... 18 divider phase offset .................................................................. 20 delay block ................................................................................. 21 outputs ........................................................................................ 21 power supply............................................................................... 22 exposed metal paddle ........................................................... 22 power management ................................................................... 22 applications..................................................................................... 23 using the ad9513 outputs for adc clock applications.... 23 lvds clock distribution .......................................................... 23 cmos clock distribution ........................................................ 23 setup pins (s0 to s10)................................................................ 24 power and grounding considerations and power supply rejection...................................................................................... 24 phase noise and jitter measurement setups........................... 25 outline dimensions ....................................................................... 26 ordering guide .......................................................................... 26 revision history 9/05revision 0: initial version
ad9513 rev. 0 | page 3 of 28 specifications typical (typ) is given for v s = 3.3 v 5%; t a = 25c, r set = 4.12 k, unless otherwise note d. minimum (min) and maximum (max) values are given over full v s and t a (?40c to +85c) variation. clock input table 1. parameter min typ max unit test conditions/comments clock input (clk) input frequency 0 1.6 ghz input sensitivity 1 150 mv p-p input common-mode voltage, v cm 1.5 1.6 1.7 v self-biased; enables ac coupling input common-mode range, v cmr 1.3 1.8 v with 200 mv p-p signal applied; dc-coupled input sensitivity, single-ended 150 mv p-p clk ac-coupled; clkb ac-b ypassed to rf ground input resistance 4.0 4.8 5.6 k self-biased input capacitance 2 pf 1 a slew rate of 1 v/ns is required to meet jitter, phase noise, and propagat ion delay specifications. clock outputs table 2. parameter min typ max unit test conditions/comments lvds clock output termination = 100 differential differential output frequency 0 800 mhz differential output voltage (v od ) 250 350 450 mv delta v od 30 mv output offset voltage (v os ) 1.125 1.23 1.375 v delta v os 25 mv short-circuit current (i sa , i sb ) 14 24 ma output shorted to gnd cmos clock output single-ended measurements; termination open single-ended complementary output on (out1b) output frequency 0 250 mhz with 5 pf load output voltage high (v oh ) v s ? 0.1 v @ 1 ma load output voltage low (v ol ) 0.1 v @ 1 ma load
ad9513 rev. 0 | page 4 of 28 timing characteristics clk input slew rate = 1 v/ns or greater. table 3. parameter min typ max unit test conditions/comments lvds termination = 100 differential output rise time, t rl 200 350 ps 20% to 80%, measured differentially output fall time, t fl 210 350 ps 80% to 20%, measured differentially propagation delay, t lvds , clk-to-lvds out delay off on out2 out0, out1, out2 divide = 1 1.03 1.29 1.62 ns divide = 2 ? 32 1.09 1.35 1.68 ns variation with temperature 0.9 ps/c out2 divide = 1 1.07 1.35 1.69 ns divide = 2 ? 32 1.13 1.41 1.75 ns variation with temperature 0.9 ps/c output skew, lvds outputs delay off on out2 out0 to out1 on same part, t skv 1 ?135 ?20 +125 ps out0 to out2 on same part, t skv 1 ?205 ?65 +90 ps all lvds outs across multiple parts, t skv_ab 2 375 ps same lvds outs across multiple parts, t skv_ab 2 300 ps cmos b outputs are inverted; termination = open output rise time, t rc 650 865 ps 20% to 80%; c load = 3 pf output fall time, t fc 650 990 ps 80% to 20%; c load = 3 pf propagation delay, t cmos , clk-to-cmos out delay off on out2 out0, out1 divide = 1 1.14 1.46 1.89 ns divide = 2 ? 32 1.19 1.51 1.94 ns variation with temperature 1 ps/c out2 divide = 1 1.20 1.53 1.97 ns divide = 2 ? 32 1.24 1.57 2.01 ns variation with temperature 1 ps/c output skew, cmos outputs delay off on out2 all cmos outs on same part, t skc 1 ?230 +135 ps all cmos outs across multiple parts, t skc_ab 2 415 ps same cmos outs across multiple parts, t skc_ab 2 330 ps lvds-to-cmos out everything the same; different logic type output skew, t skv_c 510 ps lvds to cmos on same part delay adjust (out2; lvds and cmos) s0 = 1/3 zero-scale delay time 3 0.35 ns zero-scale variation with temperature 0.20 ps/c full-scale time delay 3 1.8 ns full-scale variation with temperature ?0.38 ps/c s0 = 2/3 zero-scale delay time 3 0.48 ns zero-scale variation with temperature 0.31 ps/c full-scale time delay 3 6.0 ns full-scale variation with temperature ?1.3 ps/c
ad9513 rev. 0 | page 5 of 28 min typ max unit test conditions/comments parameter s0 = 1 zero-scale delay time 3 0.59 ns zero-scale variation with temperature 0.47 ps/c full-scale time delay 3 11.6 ns full-scale variation with temperature ?5 ps/c linearity, dnl 0.2 lsb linearity, inl 0.2 lsb 1 this is the difference between any two s imilar delay paths within a single device op erating at the same voltage and temperatur e. 2 this is the difference between any two s imilar delay paths across multiple devices op erating at the same voltage and temperatu re. 3 incremental delay; does not include propagation delay.
ad9513 rev. 0 | page 6 of 28 clock output phase noise table 4. parameter min typ max unit test conditions/comments clk-to-lvds additive phase noise clk = 622.08 mhz, out = 622.08 mhz divide ratio = 1 @ 10 hz offset ?100 dbc/hz @ 100 hz offset ?110 dbc/hz @ 1 khz offset ?118 dbc/hz @ 10 khz offset ?129 dbc/hz @ 100 khz offset ?135 dbc/hz @ 1 mhz offset ?140 dbc/hz >10 mhz offset ?148 dbc/hz clk = 622.08 mhz, out = 155.52 mhz divide ratio = 4 @ 10 hz offset ?112 dbc/hz @ 100 hz offset ?122 dbc/hz @ 1 khz offset ?132 dbc/hz @ 10 khz offset ?142 dbc/hz @ 100 khz offset ?148 dbc/hz @ 1 mhz offset ?152 dbc/hz >10 mhz offset ?155 dbc/hz clk = 491.52 mhz, out = 245.76 mhz divide ratio = 2 @ 10 hz offset ?108 dbc/hz @ 100 hz offset ?118 dbc/hz @ 1 khz offset ?128 dbc/hz @ 10 khz offset ?138 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?148 dbc/hz >10 mhz offset ?154 dbc/hz clk = 491.52 mhz, out = 122.88 mhz divide ratio = 4 @ 10 hz offset ?118 dbc/hz @ 100 hz offset ?129 dbc/hz @ 1 khz offset ?136 dbc/hz @ 10 khz offset ?147 dbc/hz @ 100 khz offset ?153 dbc/hz @ 1 mhz offset ?156 dbc/hz >10 mhz offset ?158 dbc/hz clk = 245.76 mhz, out = 245.76 mhz divide ratio = 1 @ 10 hz offset ?108 dbc/hz @ 100 hz offset ?118 dbc/hz @ 1 khz offset ?128 dbc/hz @ 10 khz offset ?138 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?148 dbc/hz >10 mhz offset ?155 dbc/hz
ad9513 rev. 0 | page 7 of 28 min typ max unit test conditions/comments parameter clk = 245.76 mhz, out = 122.88 mhz divide ratio = 2 @ 10 hz offset ?118 dbc/hz @ 100 hz offset ?127 dbc/hz @ 1 khz offset ?137 dbc/hz @ 10 khz offset ?147 dbc/hz @ 100 khz offset ?154 dbc/hz @ 1 mhz offset ?156 dbc/hz >10 mhz offset ?158 dbc/hz clk-to-cmos additive phase noise clk = 245.76 mhz, out = 245.76 mhz divide ratio = 1 @ 10 hz offset ?110 dbc/hz @ 100 hz offset ?121 dbc/hz @ 1 khz offset ?130 dbc/hz @ 10 khz offset ?140 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?149 dbc/hz >10 mhz offset ?156 dbc/hz clk = 245.76 mhz, out = 61.44 mhz divide ratio = 4 @ 10 hz offset ?125 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?143 dbc/hz @ 10 khz offset ?152 dbc/hz @ 100 khz offset ?158 dbc/hz @ 1 mhz offset ?160 dbc/hz >10 mhz offset ?162 dbc/hz clk = 78.6432 mhz, out = 78.6432 mhz divide ratio = 1 @ 10 hz offset ?122 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?140 dbc/hz @ 10 khz offset ?150 dbc/hz @ 100 khz offset ?155 dbc/hz @ 1 mhz offset ?158 dbc/hz >10 mhz offset ?160 dbc/hz clk = 78.6432 mhz, out = 39.3216 mhz divide ratio = 2 @ 10 hz offset ?128 dbc/hz @ 100 hz offset ?136 dbc/hz @ 1 khz offset ?146 dbc/hz @ 10 khz offset ?155 dbc/hz @ 100 khz offset ?161 dbc/hz >1 mhz offset ?162 dbc/hz
ad9513 rev. 0 | page 8 of 28 clock output additive time jitter table 5. parameter min typ max unit test conditions/comments lvds output additive time jitter calculated from snr of adc method clk= 400 mhz 300 fs rms lvds (out0) = 100 mhz divide ratio = 4 lvds (out1, out2) = 100 mhz interferer clk = 400 mhz 300 fs rms lvds (out0) = 100 mhz divide ratio = 4 lvds (out1, out2) = 50 mhz interferer clk = 400 mhz 305 fs rms lvds (out1) = 100 mhz divide ratio = 4 lvds (out0, out2) = 100 mhz interferer clk = 400 mhz 310 fs rms lvds (out1) = 100 mhz divide ratio = 4 lvds (out0, out2) = 50 mhz interferer clk = 400 mhz 310 fs rms lvds (out2) = 100 mhz divide ratio = 4 lvds (out0, out1) = 100 mhz interferer clk = 400 mhz 315 fs rms lvds (out2) = 100 mhz divide ratio = 4 lvds (out0, out1) = 50 mhz interferer clk = 400 mhz 345 fs rms lvds (out2) = 100 mhz divide ratio = 4 cmos (out0, out1) = 50 mhz interferer cmos output additive time jitter calculated from snr of adc method clk = 400 mhz 300 fs rms cmos (out0) = 100 mhz divide ratio = 4 lvds (out2) = 100 mhz interferer clk = 400 mhz 300 fs rms cmos (out0) = 100 mhz divide ratio = 4 cmos (out1, out2) = 50 mhz interferer clk = 400 mhz 335 fs rms cmos (out1) = 100 mhz divide ratio = 4 cmos (out0, out2) = 50 mhz interferer clk = 400 mhz 355 fs rms cmos (out2) = 100 mhz divide ratio = 4 cmos (out0, out1) = 50 mhz interferer clk = 400 mhz 340 fs rms cmos (out2) = 100 mhz divide ratio = 4 lvds (out0, out1) = 50 mhz interferer
ad9513 rev. 0 | page 9 of 28 parameter min typ max unit test conditions/comments delay block additive time jitter 1 100 mhz output; incremental additive jitter 1 delay fs = 1.8 ns fine adj. 00000 0.71 ps rms delay fs = 1.8 ns fine adj. 11111 1.2 ps rms delay fs = 6.0 ns fine adj. 00000 1.3 ps rms delay fs = 6.0 ns fine adj. 11111 2.7 ps rms delay fs = 11.6 ns fine adj. 00000 2.0 ps rms delay fs = 11.6 ns fine adj. 11111 2.8 ps rms 1 this value is incremental. that is, it is in addition to the jitter of the lvds or cmos output without the delay. to estimate the total jitter, the lvds or cmos output jitter should be added to this value using the root sum of the squares (rss) method. syncb, vref, and setup pins table 6. parameter min typ max unit test conditions/comments syncb logic high 2.7 v logic low 0.40 v capacitance 2 pf vref output voltage 0.62v s 0.76v s v minimum ? maximum from 0 ma to 1 ma load s0 to s10 levels 0 0.1v s v 1/3 0.2v s 0.45v s v 2/3 0.55v s 0.8v s v 1 0.9v s v power table 7. parameter min typ max unit test conditions/comments power-on synchronization 1 35 ms see the power-on sync section. v s transit time from 2.2 v to 3.1 v power dissipation 175 325 575 mw all three outputs on. lvds (divide = 2). no clock. does not include power dissipated in external resistors. 240 460 615 mw all three outputs on. cmos (divide = 2); 62.5 mhz out (5 pf load). 320 605 840 mw all three outputs on. cmos (divide = 2); 125 mhz out (5 pf load). power delta divider (divide = 2 to divide = 1) 15 30 45 mw for each divider. no clock. lvds output 20 50 85 mw no clock. cmos output (static) 30 40 50 mw no clock. cmos output (@ 62.5 mhz) 65 110 155 mw single-ended. at 62.5 mhz out with 5 pf load. cmos output (@ 125 mhz) 70 145 220 mw single-ended. at 125 mhz out with 5 pf load. delay block 30 45 65 mw off to 1.8 ns fs, delay word = 60; output clocking at 62.5 mhz. 1 this is the rise time of the v s supply that is required to ensure that a synchronization of the outputs occurs on power-up. the critical factor is the time it takes the v s to transition the range from 2.2 v to 3 .1 v. if the ri se time is too slow, the outputs are not synchronized.
ad9513 rev. 0 | page 10 of 28 timing diagrams clk t clk t lvds t cmos 05595-002 figure 2. clk/clkb to clock output timing, div = 1 mode 0 5595-065 differential lvds 80% 20% t rl t fl figure 3. lvds timing, differential 0 5595-066 single-ended cmos 3pf load 80% 20% t rc t fc figure 4. cmos timing, single-ended, 3 pf load
ad9513 rev. 0 | page 11 of 28 absolute maximum ratings table 8. parameter or pin with respect to min max unit vs gnd ?0.3 +3.6 v rset gnd ?0.3 v s + 0.3 v clk gnd ?0.3 v s + 0.3 v clk clkb ?1.2 +1.2 v out0, out1, out2 gnd ?0.3 v s + 0.3 v function gnd ?0.3 v s + 0.3 v status gnd ?0.3 v s + 0.3 v junction temperature 1 150 c storage temperature ?65 +150 c lead temperature (10 sec) 300 c stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. exposure to absolute maximum ratings for extended periods may affect device reliability. thermal characteristics 2 thermal resistance 32-lead lfcsp 3 ja = 36.6c/w 1 see thermal characteristics for ja . 2 thermal impedance measurements were taken on a 4-layer board in still air in accordance with eia/jesd51-7. 3 the external pad of this package must be soldered to adequate copper land on board. esd caution esd (electrostatic discharge) sensitive device. electros tatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge wi thout detection. although this product features proprietary esd protection circuitry, permanent dama ge may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality.
ad9513 rev. 0 | page 12 of 28 pin configuration and fu nction descriptions 1 vs 2 clk 3 clkb 4 vs 5 syncb 6 vref 7 s10 8 s9 18 out2b 19 out2 20 vs 21 vs 22 out1b 23 out1 24 vs 17 vs 9 s 8 1 0 s 7 1 1 s 6 1 3 s 4 1 5 s 2 1 4 s 3 1 6 s 1 1 2 s 5 2 6 v s 2 7 o u t 0 b 2 8 o u t 0 2 9 v s 3 0 v s 2 5 s 0 top view (not to scale) ad9513 3 1 g n d 3 2 r s e t 05595-005 figure 5. 32-lead lfcsp pin configuration 05595-006 1 32 8 9 25 24 16 17 the exposed paddle is an electrical and thermal connection exposed pad (bottom view) gnd figure 6. exposed paddle note that the exposed paddle on this package is an electrical connection as well as a thermal enhancement. for the device to function properly, the paddle must be soldered to a pcb land that functions as both a heat dissipation path as well as an electrical ground. table 9. pin function descriptions pin no. nemonic description 1, 4 ,17 ,20, 21, 24, 26, 29, 30 vs power supply (3.3 v). 2 clk clock input. 3 clkb complementary clock input. 5 syncb used to synchronize outputs. 6 vref provides 2/3 v s for use as one of the four logic levels on s0 to s10. 7 to16, 25 s10 to s1, s0 setup select pins. these are 4-state logic. the logic levels are v s , gnd, 1/3 v s , and 2/3 v s . the vref pin provides 2/3 v s . each pin is internally biased to 1/3 v s so that a pin requiring that logic level should be left nc (no connection). 18 out2b complementary lvds/inverted cmos output. 19 out2 lvds/cmos output. 22 out1b complementary lvds/inverted cmos output. out6 includes a delay block. 23 out1 lvds/cmos output. out6 includes a delay block. 27 out0b complementary lvds/inverted cmos output. out5 includes a delay block. 28 out0 lvds/cmos output. out5 includes a delay block. 31 gnd ground. the exposed paddle on the back of the chip is also gnd. 32 rset current set resistor to ground. nominal value = 4.12 k.
ad9513 rev. 0 | page 13 of 28 terminology phase jitter and phase noise an ideal sine wave can be thought of as having a continuous and even progression of phase with time from 0 to 360 degrees for each cycle. actual signals, however, display a certain amount of variation from ideal phase progression over time. this phenomenon is called phase jitter. although there are many causes that can contribute to phase jitter, one major component is due to random noise that is characterized statistically as being gaussian (normal) in distribution. this phase jitter leads to a spreading out of the energy of the sine wave in the frequency domain, producing a continuous power spectrum. this power spectrum is usually reported as a series of values whose units are dbc/hz at a given offset in frequency from the sine wave (carrier). the value is a ratio (expressed in db) of the power contained within a 1 hz bandwidth with respect to the power at the carrier frequency. for each measurement, the offset from the carrier frequency is also given. it is also meaningful to integrate the total power contained within some interval of offset frequencies (for example, 10 khz to 10 mhz). this is called the integrated phase noise over that frequency offset interval and can be readily related to the time jitter due to the phase noise within that offset frequency interval. phase noise has a detrimental effect on the performance of adcs, dacs, and rf mixers. it lowers the achievable dynamic range of the converters and mixers, although they are affected in somewhat different ways. time jitter phase noise is a frequency domain phenomenon. in the time domain, the same effect is exhibited as time jitter. when observing a sine wave, the time of successive zero crossings is seen to vary. for a square wave, the time jitter is seen as a displacement of the edges from their ideal (regular) times of occurrence. in both cases, the variations in timing from the ideal are the time jitter. since these variations are random in nature, the time jitter is specified in units of seconds root mean square (rms) or 1 sigma of the gaussian distribution. time jitter that occurs on a sampling clock for a dac or an adc decreases the snr and dynamic range of the converter. a sampling clock with the lowest possible jitter provides the highest performance from a given converter. additive phase noise it is the amount of phase noise that is attributable to the device or subsystem being measured. the phase noise of any external oscillators or clock sources has been subtracted. this makes it possible to predict the degree to which the device as the total system phase noise when used in conjunction with the various oscillators and clock sources, each of which contribute their own phase noise to the total. in many cases, the phase noise of one element dominates the system phase noise. additive time jitter it is the amount of time jitter that is attributable to the device or subsystem being measured. the time jitter of any external oscillators or clock sources has been subtracted. this makes it possible to predict the degree to which the device will affect the total system time jitter when used in conjunction with the various oscillators and clock sources, each of which contribute their own time jitter to the total. in many cases, the time jitter of the external oscillators and clock sources dominates the system time jitter.
ad9513 rev. 0 | page 14 of 28 typical performance characteristics 05595-050 output frequency (mhz) power (w) 800 600 400 200 0.1 0.4 0.3 0.2 3 lvds (div on) 3 lvds (div = 1) figure 7. power vs. frequencylvds start 300khz stop 5ghz 05595-097 figure 8. clk smith chart (evaluation board) 05595-051 output frequency (mhz) power (w) 120 100 80 60 40 20 0 0.1 0.7 0.6 0.5 0.4 0.3 0.2 3 cmos (div on) 3 cmos (div off) figure 9. power vs. frequencycmos
ad9513 rev. 0 | page 15 of 28 vert 100mv/div horiz 500ps/div 0 5595-010 figure 10. lvds differential output @ 800 mhz vert 500mv/div horiz 1ns/div 05595-011 figure 11. cmos single-ended output @ 250 mhz with 10 pf load output frequency (mhz) differential swing (mv p-p) 100 900 700 500 300 500 750 700 650 600 550 05595-013 figure 12. lvds differential output swing vs. frequency output frequency (mhz) output (v pk ) 06 500 400 300 200 100 0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 2pf 10pf 20pf 0 0 05595-014 figure 13. cmos single-ended output swing vs. frequency and load
ad9513 rev. 0 | page 16 of 28 05595-048 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 80 ?90 ?110 ?100 ?120 ?130 ?140 ?150 ?160 figure 14. additive phase noiselvds div 1, 245.76 mhz 05595-045 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 100 ?110 ?120 ?130 ?140 ?150 ?160 figure 15. additive phase noisecmos div 1, 245.76 mhz 05595-049 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 80 ?90 ?110 ?100 ?120 ?130 ?140 ?150 ?160 figure 16. additive phase noiselvds div2, 122.88 mhz 05595-046 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 100 ?110 ?120 ?130 ?140 ?150 ?160 figure 17. additive phase noisecmos div4, 61.44 mhz
ad9513 rev. 0 | page 17 of 28 functional description overall the ad9513 provides for the distribution of its input clock on up to three outputs. each output can be set to either lvds or cmos logic levels. each output has its own divider that can be set for a divide ratio selected from a list of integer values from 1 (bypassed) to 32. out2 includes an analog delay block that can be set to add an additional delay of 1.8 ns, 6.0 ns, or 11.6 ns full scale, each with 16 levels of fine adjustment. clk, clkbdifferential clock input the clk and clkb pins are differential clock input pins. this input works up to 1600 mhz. the jitter performance is degraded by a slew rate below 1 v/ns. the input level should be between approximately 150 mv p-p to no more than 2 v p-p. anything greater can result in turning on the protection diodes on the input pins. see figure 18 for the clk equivalent input circuit. this input is fully differential and self-biased. the signal should be ac- coupled using capacitors. if a single-ended input must be used, this can be accommodated by ac coupling to one side of the differential input only. the other side of the input should be bypassed to a quiet ac ground by a capacitor. 2.5k ? 5k? 5k? 2.5k ? clkb clk v s clock input stage 05595-021 figure 18. clock input equivalent circuit synchronization power-on sync a power-on sync (pos) is issued when the v s power supply is turned on to ensure that the outputs start in synchronization. the power-on sync works only if the v s power supply transi- tions the region from 2.2 v to 3.1 v within 35 ms. the pos can occur up to 65 ms after v s crosses 2.2 v. only outputs which are not divide = 1 are synchronized. clk out 0v 3.3v 2.2v 3.1v v s clock frequency is example only divide = 2 phase = 0 < 65ms internal sync node 35ms max 05595-094 figure 19. power-on sync timing syncb if the setup configuration of the ad9513 is changed during operation, the outputs can become unsynchronized. the outputs can be resynchronized to each other at any time. synchronization occurs when the syncb pin is pulled low and released. the clock outputs (except where divide = 1) are forced into a fixed state (determined by the divide and phase settings) and held there in a static condition, until the syncb pin is returned to high. upon release of the syncb pin, after four cycles of the clock signal at clk, all outputs continue clocking in synchronicity (except where divide = 1). when divide = 1 for an output, that output is not affected by syncb. clk s yncb out 3 clk cycle s 4 clk cycle s example: divide 8 phase = 0 example divide ratio phase = 0 05595-093 figure 20. syncb timing with clock present 4 clk cycles clk out syncb depends on previous state and divide ratio depends on previous state example divide ratio phase = 0 min 5ns 05595-092 figure 21. syncb timing with no clock present the outputs of the ad9513 can be synchronized by using the syncb pin. synchronization aligns the phases of the clock outputs, respecting any phase offset that has been set on an outputs divider. syncb 05595-022 figure 22. syncb equi valent input circuit
ad9513 rev. 0 | page 18 of 28 synchronization is initiated by pulling the syncb pin low for a minimum of 5 ns. the input clock does not have to be present at the time the command is issued. the synchronization occurs after four input clock cycles. the synchronization applies to clock outputs ? that are not turned off ? where the divider is not divide = 1 (divider bypassed) an output with its divider set to divide = 1 (divider bypassed) is always synchronized with the input clock, with a propagation delay. the syncb pin must be pulled up for normal operation. do not let the syncb pin float. rset resistor the internal bias currents of the ad9513 are set by the r set resistor. this resistor should be as close as possible to the value given as a condition in the specifications section (r set = 4.12 k). this is a standard 1% resistor value and should be readily obtainable. the bias currents set by this resistor determine the logic levels and operating conditions of the internal blocks of the ad9513. the performance figures given in the specifications section assume that this resistor value is used for r set . vref the vref pin provides a voltage level of ? v s . this voltage is one of the four logic levels used by the setup pins (s0 to s10). these pins set the operation of the ad9513. the vref pin provides sufficient drive capability to drive as many of the setup pins as necessary, up to all on a single part. the vref pin should be used for no other purpose. setup configuration the specific operation of the ad9513 is set by the logic levels applied to the setup pins (s10 to s0). these pins use four-state logic. the logic levels used are v s and gnd, plus ? v s and ? v s . the ? v s level is provided by the internal self-biasing on each of the setup pins (s10 to s0). this is the level seen by a setup pin that is left not connected (nc). the ? v s level is provided by the vref pin. all setup pins requiring the ?v s level must be tied to the vref pin. setup pin s0 to s10 60k ? 30k ? v s 05595-023 figure 23. setup pin (s0 to s10) equivalent circuit the ad9513 operation is determined by the combination of logic levels present at the setup pins. the setup configurations for the ad9513 are shown in table 11 to table 16 . the four logic levels are referred to as 0, ?, ?, and 1. these numbers represent the fraction of the v s voltage that defines the logic levels. see the setup pin thresholds in tabl e 6 . the meaning of some of the pin settings is changed by the settings of other pins. for example, s0 determines whether s3, and s4 sets out2 delay (s0 0) or out2 phase (s0 = 0). s2 indicates which outputs are in use, as shown in table 10 . this allows the same pins (s5 and s6, s7 and s8) to determine the settings for two different outputs, depending on which outputs are in use. table 10. s2 indicates which outputs are in use s2 outputs 0 out2 off 1/3 all outputs on 2/3 out0 off 1 out1 off the fine delay values set by s3 and s4 (when the delay is being used, s0 0) are fractions of the full-scale delay. note that the longest setting is 15/16 of full scale. the full-scale delay times are given in table 3 . to determine the actual delay, take the fraction corresponding to the fine delay setting and multiply by the full-scale value set by tabl e 3 corresponding to the s0 value and add the lvds or cmos propagation delay time (see table 3 ). the full-scale delay times shown in table 11 , and referred to elsewhere, are nominal time values. the value at s2 also determines whether s5 and s6 set out2 divide (s2 0) or out1 phase (s2 = 0). in addition, s2 determines whether s7 and s8 set out1 divide (s2 1) or out2 phase (s2 = 1 and s0 0). in addition, the value of s2 determines whether s9 and s10 set out0 divide (s2 2/3) or out2 divide (s2 = 2/3).
ad9513 rev. 0 | page 19 of 28 table 11. output delay full scale s0 delay 0 bypass 1/3 1.8 ns 2/3 6.0 ns 1 11.6 ns table 12. output logic configuration s1 s2 out0 out1 out2 0 0 off lvds off 1/3 0 cmos cmos off 2/3 0 lvds lvds off 1 0 lvds cmos off 0 1/3 cmos cmos cmos 1/3 1/3 lvds lvds lvds 2/3 1/3 lvds lvds cmos 1 1/3 cmos cmos lvds 0 2/3 off off off 1/3 2/3 off off lvds 2/3 2/3 off off cmos 1 2/3 off cmos off 0 1 lvds off cmos 1/3 1 cmos off lvds 2/3 1 lvds off lvds 1 1 cmos off cmos table 13. out2 delay or phase s3 s4 out2 delay (s0 0) out2 phase (s0 = 0) 0 0 0 0 1/3 0 1/16 1 2/3 0 1/8 2 1 0 3/16 3 0 1/3 1/4 4 1/3 1/3 5/16 5 2/3 1/3 3/8 6 1 1/3 7/16 7 0 2/3 1/2 8 1/3 2/3 9/16 9 2/3 2/3 5/8 10 1 2/3 11/16 11 0 1 3/4 12 1/3 1 13/16 13 2/3 1 7/8 14 1 1 15/16 15 table 14. out2 divide or out1 phase s5 s6 out2 divide (duty cycle 1 ) (s2 0) out1 phase (s2 = 0) 0 0 1 0 1/3 0 2 (50%) 1 2/3 0 3 (33%) 2 1 0 4 (50%) 3 0 1/3 5 (40%) 4 1/3 1/3 6 (50%) 5 2/3 1/3 8 (50%) 6 1 1/3 9 (44%) 7 0 2/3 10 (50%) 8 1/3 2/3 12 (50%) 9 2/3 2/3 15 (47%) 10 1 2/3 16 (50%) 11 0 1 18 (50%) 12 1/3 1 24 (50%) 13 2/3 1 30 (50%) 14 1 1 32 (50%) 15 1 duty cycle is the clock signal high time divided by the total period. table 15. out1 divide or out2 phase s7 s8 out1 divide (duty cycle 1 ) (s2 1) out2 phase (s2 = 1 and s0 0) 0 0 1 0 1/3 0 2 (50%) 1 2/3 0 3 (33%) 2 1 0 4 (50%) 3 0 1/3 5 (40%) 4 1/3 1/3 6 (50%) 5 2/3 1/3 8 (50%) 6 1 1/3 9 (44%) 7 0 2/3 10 (50%) 8 1/3 2/3 12 (50%) 9 2/3 2/3 15 (47%) 10 1 2/3 16 (50%) 11 0 1 18 (50%) 12 1/3 1 24 (50%) 13 2/3 1 30 (50%) 14 1 1 32 (50%) 15 1 duty cycle is the clock signal high time divided by the total period.
ad9513 rev. 0 | page 20 of 28 table 16. out0 divide or out2 divide s9 s10 out0 divide (duty cycle 1 ) s2 2/3 out2 divide (duty cycle 1 ) s2 = 2/3 0 0 1 7 (43%) 1/3 0 2 (50%) 11 (45%) 2/3 0 3 (33%) 13 (46%) 1 0 4 (50%) 14 (50%) 0 1/3 5 (40%) 17 (47%) 1/3 1/3 6 (50%) 19 (47%) 2/3 1/3 8 (50%) 20 (50%) 1 1/3 9 (44%) 21 (48%) 0 2/3 10 (50%) 22 (50%) 1/3 2/3 12 (50%) 23 (48%) 2/3 2/3 15 (47%) 25 (48%) 1 2/3 16 (50%) 26 (50%) 0 1 18 (50%) 27 (48%) 1/3 1 24 (50%) 28 (50%) 2/3 1 30 (50%) 29 (48%) 1 1 32 (50%) 31 (48%) 1 duty cycle is the clock signal high time divided by the total period. divider phase offset the phase offset of out1 and out2 can be selected (see table 13 to table 15 ). this allows the relative phase of the outputs to be set. after a sync operation (see the synchronization section), the phase offset word of each divider determines the number of input clock (clk) cycles to wait before initiating a clock output edge. by giving each divider a different phase offset, output-to- output delays can be set in increments of the fast clock period, t clk . figure 24 shows four cases, each with the divider set to divide = 4. by incrementing the phase offset from 0 to 3, the output is offset from the initial edge by a multiple of t clk . 01 4 123 5 9 678 10 14 11 12 13 5 t clk clock input clk divider output div = 4 phase = 0 phase = 1 phase = 2 phase = 3 t clk 2 t clk 3 t clk 05595-024 figure 24. phase offsetdivider set for divide = 4, phase set from 0 to 2 for example: clk = 491.52 mhz t clk = 1/491.52 = 2.0345 ns for divide = 4: phase offset 0 = 0 ns phase offset 1 = 2.0345 ns phase offset 2 = 4.069 ns phase offset 3 = 6.104 ns the outputs can also be described as: phase offset 0 = 0 phase offset 1 = 90 phase offset 2 = 180 phase offset 3 = 270 setting the phase offset to phase = 4 results in the same relative phase as phase = 0 or 360. the resolution of the phase offset is set by the fast clock period (t clk ) at clk. the maximum unique phase offset is less than the divide ratio, up to a phase offset of 15. phase offsets can be related to degrees by calculating the phase step for a particular divide ratio: phase step = 360/ divide ratio using some of the same examples: divide = 4 phase step = 360/4 = 90 unique phase offsets in degrees are phase = 0, 90, 180, 270 divide = 9 phase step = 360/9 = 40 unique phase offsets in degrees are phase = 0, 40, 80, 120, 160, 200, 240, 280, 320
ad9513 rev. 0 | page 21 of 28 delay block out2 includes an analog delay element that gives variable time delays (t) in the clock signal passing through that output. n ?select lvds cmos ? t mux output driver fine delay adjust (16 steps) full scale : 1.5ns, 5ns, 10ns clock input out1 only 05595-025 figure 25. analog delay block the amount of delay that can be used is determined by the output frequency. the amount of delay is limited to less than one-half cycle of the clock period. for example, for a 10 mhz clock, the delay can extend to the full 11.6 ns maximum. however, for a 100 mhz clock, the maximum delay is less than 5 ns (or half of the period). the ad9513 allows for the selection of three full-scale delays, 1.8 ns, 6.0 ns, and 11.6 ns, set by delay full-scale (see tabl e 11 ). each of these full-scale delays can be scaled by 16 fine adjustment values, which are set by the delay word (see tabl e 13 ). the delay block adds some jitter to the output. this means that the delay function should be used primarily for clocking digital chips, such as fpga, asic, duc, and ddc, rather than for supplying a sample clock for data converters. the jitter is higher for longer full scales because the delay block uses a ramp and trip points to create the variable delay. a longer ramp means more noise has a chance of being introduced. when the delay block is off (bypassed), it is also powered down. outputs each of the three ad9513 outputs can be selected either as lvds differential outputs or as pairs of cmos single-ended outputs. if selected as cmos, the out is a noninverted, single- ended output, and outb is an inverted, single-ended output. outb out 3 .5m a 3 .5m a 05595-027 figure 26. lvds output simplified equivalent circuit 05595-028 out1/ out1b v s figure 27. cmos equiva lent output circuit
ad9513 rev. 0 | page 22 of 28 power supply the ad9513 requires a 3.3 v 5% power supply for v s . the tables in the specifications section give the performance expected from the ad9513 with the power supply voltage within this range. in no case should the absolute maximum range of ?0.3 v to +3.6 v, with respect to gnd, be exceeded on pin vs. good engineering practice should be followed in the layout of power supply traces and the ground plane of the pcb. the power supply should be bypassed on the pcb with adequate capacitance (>10 f). the ad9513 should be bypassed with adequate capacitors (0.1 f) at all power pins as close as possible to the part. the layout of the ad9513 evaluation board (ad9513/pcb) is a good example. exposed metal paddle the exposed metal paddle on the ad9513 package is an electrical connection, as well as a thermal enhancement. for the device to function properly, the paddle must be properly attached to ground (gnd). the exposed paddle of the ad9513 package must be soldered down. the ad9513 must dissipate heat through its exposed paddle. the pcb acts as a heat sink for the ad9513. the pcb attachment must provide a good thermal path to a larger heat dissipation area, such as a ground plane on the pcb. this requires a grid of vias from the top layer down to the ground plane (see figure 28 ).the ad9513 evaluation board (ad9513/pcb)provides a good example of how the part should be attached to the pcb. 05595-035 vias to gnd plane figure 28. pcb land for attaching exposed paddle power management in some cases, the ad9513 can be configured to use less power by turning off functions that are not being used. the power-saving options include the following: ? a divider is powered down when set to divide = 1 (bypassed). ? adjustable delay block on out2 is powered down when in off mode (s0 = 0). ? an unneeded output can be powered down (see table 12 ). this also powers down the divider for that output.
ad9513 rev. 0 | page 23 of 28 applications using the ad9513 outputs for adc clock applications any high speed, analog-to-digital converter (adc) is extremely sensitive to the quality of the sampling clock provided by the user. an adc can be thought of as a sampling mixer; any noise, distortion, or timing jitter on the clock is combined with the desired signal at the a/d output. clock integrity requirements scale with the analog input frequency and resolution, with higher analog input frequency applications at 14-bit resolution being the most stringent. the theoretical snr of an adc is limited by the adc resolution and the jitter on the sampling clock. considering an ideal adc of infinite resolution where the step size and quantization error can be ignored, the available snr can be expressed approximately by ? ? ? ? ? ? ? ? = j ft snr 2 1 log20 where f is the highest analog frequency being digitized. t j is the rms jitter on the sampling clock. figure 29 shows the required sampling clock jitter as a function of the analog frequency and effective number of bits (enob). f a full-scale sine wave analog frequency (mhz) snr (db) enob 10 1k 100 30 40 50 60 70 80 90 100 110 6 8 10 12 14 16 18 t j = 1 0 0 f s 2 0 0 f s 4 0 0 f s 1 p s 2 p s 1 0 p s snr = 20log 1 2 f a t j 05595-091 figure 29. enob and snr vs. analog input frequency see application note an-756 and application note an-501 at www.analog.com . many high performance adcs feature differential clock inputs to simplify the task of providing the required low jitter clock on a noisy pcb. (distributing a single-ended clock on a noisy pcb can result in coupled noise on the sample clock. differential distribution has inherent common-mode rejection that can provide superior clock performance in a noisy environment.) the ad9513 features lvds outputs that provide differential clock outputs, which enable clock solutions that maximize converter snr performance. the input requirements of the adc (differential or single-end ed, logic level, termination) should be considered when selecting the best clocking/ converter solution. lvds clock distribution the ad9513 provides three clock outputs that are selectable as either cmos or lvds levels. lvds uses a current mode output stage. the current is 3.5 ma, which yields 350 mv output swing across a 100 resistor. the lvds outputs meet or exceed all ansi/tia/eia-644 specifications. a recommended termination circuit for the lvds outputs is shown in figure 30 . v s lvds 100? differential (coupled) v s lvds 100? 05595-032 figure 30. lvds output termination see application note an-586 at www.analog.com for more information on lvds. cmos clock distribution the ad9513 provides three outputs that are selectable as either cmos or lvds levels. when selected as cmos, an output provides for driving devices requiring cmos level logic at their clock inputs. whenever single-ended cmos clocking is used, some of the following general guidelines should be used. point-to-point nets should be designed such that a driver has one receiver only on the net, if possible. this allows for simple termination schemes and minimizes ringing due to possible mismatched impedances on the net. series termination at the source is generally required to provide transmission line matching and/or to reduce current transients at the driver. the value of the resistor is dependent on the board design and timing requirements (typically 10 to 100 is used). cmos outputs are also limited in terms of the capacitive load or trace length that they can drive. typically, trace lengths less than 3 inches are recommended to preserve signal rise/fall times and preserve signal integrity. 10? microstrip gnd 5pf 60.4 ? 1.0 inch cmos 0 5595-033 figure 31. series termination of cmos output
ad9513 rev. 0 | page 24 of 28 termination at the far end of the pcb trace is a second option. the cmos outputs of the ad9513 do not supply enough current to provide a full voltage swing with a low impedance resistive, far-end termination, as shown in figure 32 . the far-end termination network should match the pcb trace impedance and provide the desired switching point. the reduced signal swing may still meet receiver input requirements in some applications. this can be useful when driving long trace lengths on less critical nets. 50? 10? out1/out1b selected as cmos v s cmos 3pf 100? 100? 05595-034 figure 32. cmos output wi th far-end termination because of the limitations of single-ended cmos clocking, consider using differential outputs when driving high speed signals over long traces. the ad9513 offers lvds outputs that are better suited for driving long traces where the inherent noise immunity of differential signaling provides superior performance for clocking converters. setup pins (s0 to s10) the setup pins that require a logic level of ? v s (internal self- bias) should be tied together and bypassed to ground via a capacitor. the setup pins that require a logic level of ? v s should be tied together, along with the vref pin, and bypassed to ground via a capacitor. power and grounding considerations and power supply rejection many applications seek high speed and performance under less than ideal operating conditions. in these application circuits, the implementation and construction of the pcb is as important as the circuit design. proper rf techniques must be used for device selection, placement, and routing, as well as power supply bypassing and grounding to ensure optimum performance.
ad9513 rev. 0 | page 25 of 28 phase noise and jitter measurement setups a d 9 5 1 3 c l k o u t 1 o u t 1 b balun term term amp +28db zfl1000vh2 attenuator ?12db evaluation board a d 9 5 1 3 c l k o u t 1 o u t 1 b balun term term amp +28db zfl1000vh2 attenuator ?7db sig in ref in evaluation board wenzel oscillator 0 splitter zesc-2-11 variable delay colby pdl30a 0.01ns step to 10ns agilent e5500b phase noise measurement system 05595-041 figure 33. additive phase noise measurement configuration a d 9 5 1 3 c l k o u t 1 o u t 1 b balun term clk analog source term evaluation board wenzel oscillator wenzel oscillator data capture card fifo fft pc adc snr t j_rms 05595-042 figure 34. jitter determination by measuring snr of adc () () [] a_pk a dnl thermal on quantizati snr a_rms j_rms vf bwsnd v t + + ?? ? ? ? ? ? ? ? ? = where: t j_rms is the rms time jitter. snr is the signal-to-noise ratio. snd is the source noise density in nv/hz. bw is the snd filter bandwidth. v a is the analog source voltage. f a is the analog frequency. the terms are the quantization, thermal, and dnl errors.
ad9513 rev. 0 | page 26 of 28 outline dimensions compliant to jedec standards mo-220-vhhd-2 0.30 0.23 0.18 0.20 ref 0.80 max 0.65 typ 0.05 max 0.02 nom 12 max 1.00 0.85 0.80 seating plane coplanarity 0.08 1 32 8 9 25 24 16 17 0.50 0.40 0.30 3.50 ref 0.50 bsc pin 1 indicator top view 5.00 bsc sq 4.75 bsc sq 3.25 3.10 sq 2.95 pin 1 indicator 0.60 max 0.60 max 0.25 min exposed pad (bottom view) figure 35. 32-lead lead frame chip scale package [lfcsp_vq] 5 mm 5 mm body, very thin quad (cp-32-2) dimensions shown in millimeters ordering guide model temperature range package description package option ad9513bcpz 1 ?40c to +85c 32-lead lfcsp_vq cp-32-2 ad9513bcpz-reel7 1 ?40c to +85c 32-lead lfcsp_vq cp-32-2 ad9513/pcb evaluation board 1 z = pb-free part.
ad9513 rev. 0 | page 27 of 28 notes
ad9513 rev. 0 | page 28 of 28 notes ? 2005 analog devices, inc. all rights reserved. trademarks and registered trademarks are the property of their respective owners. d05595C0C9/05(0)

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